Integrated circuit devices configured to control discharge of a control gate voltage

ABSTRACT

Integrated circuit devices include a first node, a second node, a transistor connected between the first node and the second node, a current path between a control gate of the transistor and the second node, and a controller configured to concurrently discharge a voltage level of the first node and a voltage level of the second node, monitor a representation of a voltage difference between the voltage level of the first node and a voltage level of the control gate of the transistor while discharging the voltage level of the first node and discharging the voltage level of the second node, activate the current path if the voltage difference is deemed to be greater than a first value, and deactivate the current path if the voltage difference is deemed to be less than a second value.

RELATED APPLICATIONS

This application is a Continuation of U.S. patent application Ser. No. 15/866,982, filed Jan. 10, 2018, titled “CONTROLLING DISCHARGE OF A CONTROL GATE VOLTAGE,” now U.S. Pat. No. 10,317,320, issued on Jul. 9, 2019 and claims the benefit of U.S. Provisional Patent Application Ser. No. 62/610,972, filed Dec. 28, 2017 and titled, “CONTROLLING DISCHARGE OF A CONTROL GATE VOLTAGE,” which are commonly assigned and incorporated by reference herein in their entirety.

TECHNICAL FIELD

The present disclosure relates generally to memory and, in particular, in one or more embodiments, the present disclosure relates to methods of operating memory for controlling discharge of a control gate voltage, e.g., during or following an erase operation.

BACKGROUND

Integrated circuit devices traverse a broad range of electronic devices. One particular type include memory devices, oftentimes referred to simply as memory. Memory devices are typically provided as internal, semiconductor, integrated circuit devices in computers or other electronic devices. There are many different types of memory including random-access memory (RAM), read only memory (ROM), dynamic random access memory (DRAM), synchronous dynamic random access memory (SDRAM), and flash memory.

Flash memory has developed into a popular source of non-volatile memory for a wide range of electronic applications. Flash memory typically use a one-transistor memory cell that allows for high memory densities, high reliability, and low power consumption. Changes in threshold voltage (Vt) of the memory cells, through programming (which is often referred to as writing) of data storage structures (e.g., floating gates or charge traps) or other physical phenomena (e.g., phase change or polarization), determine the data state (e.g., data value) of each memory cell. Common uses for flash memory and other non-volatile memory include personal computers, personal digital assistants (PDAs), digital cameras, digital media players, digital recorders, games, appliances, vehicles, wireless devices, mobile telephones, and removable memory modules, and the uses for non-volatile memory continue to expand.

A NAND flash memory is a common type of flash memory device, so called for the logical form in which the basic memory cell configuration is arranged. Typically, the array of memory cells for NAND flash memory is arranged such that the control gate of each memory cell of a row of the array is connected together to form an access line, such as a word line. Columns of the array include strings (often termed NAND strings) of memory cells connected together in series between a pair of select gates, e.g., a source select transistor and a drain select transistor. Each source select transistor may be connected to a source, while each drain select transistor may be connected to a data line, such as column bit line. Variations using more than one select gate between a string of memory cells and the source, and/or between the string of memory cells and the data line, are known.

In programming memory, memory cells may generally be programmed as what are often termed single-level cells (SLC) or multiple-level cells (MLC). SLC may use a single memory cell to represent one digit (e.g., bit) of data. For example, in SLC, a Vt of 2.5V might indicate a programmed memory cell (e.g., representing a logical 0) while a Vt of −0.5V might indicate an erased cell (e.g., representing a logical 1). An MLC uses more than two Vt ranges, where each Vt range indicates a different data state. Multiple-level cells can take advantage of the analog nature of a traditional charge storage cell by assigning a bit pattern to a specific Vt range. While MLC typically uses a memory cell to represent one data state of a binary number of data states (e.g., 4, 8, 16, . . . ), a memory cell operated as MLC may be used to represent a non-binary number of data states. For example, where the MLC uses three Vt ranges, two memory cells might be used to collectively represent one of eight data states.

In erasing memory, memory cells might be erased by grounding access lines of a block of memory cells while applying a relatively high erase voltage (e.g., about 20V or more) to a source and data lines of the block of memory cells, and thus to the channels of those memory cells, to remove charge from their data storage structures. Although voltage levels of an erase operation may be well controlled as voltages are applied, their discharge may be less controlled.

BRIEF DESCRIPTION OF THE DRAWINGS

FIG. 1 is a simplified block diagram of a memory in communication with a processor as part of an electronic system, according to an embodiment.

FIGS. 2A-2B are schematics of portions of an array of memory cells as could be used in a memory of the type described with reference to FIG. 1.

FIG. 3 is a schematic illustrating circuitry for selective connection of a data line, for an array of memory cells as could be used in a memory of the type described with reference to FIG. 1, to a source or other circuitry of the memory.

FIG. 4 is a block schematic of circuitry for selectively controlling discharge of a control gate voltage in accordance with an embodiment.

FIG. 5 is a timing diagram for use in describing operation of the circuitry of FIG. 4 in accordance with an embodiment.

FIG. 6 is a flowchart of a method of operating a memory in accordance with an embodiment.

FIG. 7 is a flowchart of a method of operating a memory in accordance with an embodiment.

DETAILED DESCRIPTION

In the following detailed description, reference is made to the accompanying drawings that form a part hereof, and in which is shown, by way of illustration, specific embodiments. In the drawings, like reference numerals describe substantially similar components throughout the several views. Other embodiments may be utilized and structural, logical and electrical changes may be made without departing from the scope of the present disclosure. The following detailed description is, therefore, not to be taken in a limiting sense.

The term “semiconductor” used herein can refer to, for example, a layer of material, a wafer, or a substrate, and includes any base semiconductor structure. “Semiconductor” is to be understood as including silicon-on-sapphire (SOS) technology, silicon-on-insulator (SOI) technology, thin film transistor (TFT) technology, doped and undoped semiconductors, epitaxial layers of a silicon supported by a base semiconductor structure, as well as other semiconductor structures well known to one skilled in the art. Furthermore, when reference is made to a semiconductor in the following description, previous process steps may have been utilized to form regions/junctions in the base semiconductor structure, and the term semiconductor can include the underlying layers containing such regions/junctions.

The term “conductive” as used herein, as well as its various related forms, e.g., conduct, conductively, conducting, conduction, conductivity, etc., refers to electrically conductive unless otherwise apparent from the context. Similarly, the term “connecting” as used herein, as well as its various related forms, e.g., connect, connected, connection, etc., refers to electrically connecting unless otherwise apparent from the context.

FIG. 1 is a simplified block diagram of a first apparatus (e.g., an integrated circuit device), in the form of a memory (e.g., memory device) 100, in communication with a second apparatus, in the form of a processor 130, as part of a third apparatus, in the form of an electronic system, according to an embodiment. Some examples of electronic systems include personal computers, personal digital assistants (PDAs), digital cameras, digital media players, digital recorders, games, appliances, vehicles, wireless devices, cellular telephones and the like. The processor 130, e.g., a controller external to the memory device 100, may be a memory controller or other external host device.

Memory device 100 includes an array of memory cells 104 logically arranged in rows and columns. Memory cells of a logical row are typically connected to the same access line (commonly referred to as a word line) while memory cells of a logical column are typically selectively connected to the same data line (commonly referred to as a bit line). A single access line may be associated with more than one logical row of memory cells and a single data line may be associated with more than one logical column. Memory cells (not shown in FIG. 1) of at least a portion of array of memory cells 104 are capable of being programmed to one of at least two data states.

A row decode circuitry 108 and a column decode circuitry 110 are provided to decode address signals. Address signals are received and decoded to access the array of memory cells 104. Memory device 100 also includes input/output (I/O) control circuitry 112 to manage input of commands, addresses and data to the memory device 100 as well as output of data and status information from the memory device 100. An address register 114 is in communication with I/O control circuitry 112 and row decode circuitry 108 and column decode circuitry 110 to latch the address signals prior to decoding. A command register 124 is in communication with I/O control circuitry 112 and control logic 116 to latch incoming commands. A trim register 128 may be in communication with the control logic 116 to store trim settings. Although depicted as a separate storage register, trim register 128 may represent a portion of the array of memory cells 104. Trim settings are generally values used by an integrated circuit device to define values of voltage levels, control signals, timing parameters, quantities, options, etc. to be used during operation of that integrated circuit device.

A controller (e.g., the control logic 116 internal to the memory device 100) controls access to the array of memory cells 104 in response to the commands and generates status information for the external processor 130, i.e., control logic 116 is configured to perform access operations (e.g., read operations, program operations and/or erase operations) and other operations in accordance with embodiments described herein. The control logic 116 is in communication with row decode circuitry 108 and column decode circuitry 110 to control the row decode circuitry 108 and column decode circuitry 110 in response to the addresses.

Control logic 116 may also be in communication with a cache register 118. Cache register 118 may latch data, either incoming or outgoing, as directed by control logic 116 to temporarily store data while the array of memory cells 104 is busy writing or reading, respectively, other data. During a program operation (e.g., write operation), data may be passed from the cache register 118 to data register 120 for transfer to the array of memory cells 104; then new data may be latched in the cache register 118 from the I/O control circuitry 112. During a read operation, data may be passed from the cache register 118 to the I/O control circuitry 112 for output to the external processor 130; then new data may be passed from the data register 120 to the cache register 118. The cache register 118 and/or the data register 120 may form (e.g., may form a portion of) a page buffer of the memory device 100. A page buffer may further include sensing devices (not shown) to sense a data state of a memory cell of the array of memory cells 104. A status register 122 is in communication with I/O control circuitry 112 and control logic 116 to latch the status information for output to the processor 130.

Memory device 100 receives control signals at control logic 116 from processor 130 over a control link 132. The control signals might include a chip enable CE#, a command latch enable CLE, an address latch enable ALE, a write enable WE#, a read enable RE#, and a write protect WP#. Additional or alternative control signals (not shown) may be further received over control link 132 depending upon the nature of the memory device 100. Memory device 100 receives command signals (which represent commands), address signals (which represent addresses), and data signals (which represent data) from processor 130 over a multiplexed input/output (I/O) bus 134 and outputs data to processor 130 over I/O bus 134.

For example, the commands may be received over input/output (I/O) pins [7:0] of I/O bus 134 at I/O control circuitry 112 and may be written into command register 124. The addresses may be received over input/output (I/O) pins [7:0] of I/O bus 134 at I/O control circuitry 112 and may be written into address register 114. The data may be received over input/output (I/O) pins [7:0] for an 8-bit device or input/output (I/O) pins [15:0] for a 16-bit device at I/O control circuitry 112 and may be written into cache register 118. The data may be subsequently written into data register 120 for programming the array of memory cells 104. For another embodiment, cache register 118 may be omitted, and the data may be written directly into data register 120. Data may also be output over input/output (I/O) pins [7:0] for an 8-bit device or input/output (I/O) pins [15:0] for a 16-bit device. The I/O bus 134 might further include complementary data strobes DQS and DQSN that may provide a synchronous reference for data input and output. Although reference may be made to I/O pins, they may include any conductive node providing for electrical connection to the memory device 100 by an external device (e.g., processor 130), such as conductive pads or conductive bumps as are commonly used.

It will be appreciated by those skilled in the art that additional circuitry and signals can be provided, and that the memory device 100 of FIG. 1 has been simplified. It should be recognized that the functionality of the various block components described with reference to FIG. 1 may not necessarily be segregated to distinct components or component portions of an integrated circuit device. For example, a single component or component portion of an integrated circuit device could be adapted to perform the functionality of more than one block component of FIG. 1. Alternatively, one or more components or component portions of an integrated circuit device could be combined to perform the functionality of a single block component of FIG. 1.

Additionally, while specific I/O pins are described in accordance with popular conventions for receipt and output of the various signals, it is noted that other combinations or numbers of I/O pins may be used in the various embodiments.

FIG. 2A is a schematic of a portion of an array of memory cells 200A as could be used in a memory of the type described with reference to FIG. 1, e.g., as a portion of array of memory cells 104. Memory array 200A includes access lines, such as word lines 202 ₀ to 202 _(N), and data lines, such as bit lines 204 ₀ to 204 _(M). The word lines 202 may be connected to global access lines (e.g., global word lines), not shown in FIG. 2A, in a many-to-one relationship. For some embodiments, memory array 200A may be formed over a semiconductor that, for example, may be conductively doped to have a conductivity type, such as a p-type conductivity, e.g., to form a p-well, or an n-type conductivity, e.g., to form an n-well.

Memory array 200A might be arranged in rows (each corresponding to a word line 202) and columns (each corresponding to a bit line 204). Each column may include a string of series-connected memory cells (e.g., non-volatile memory cells), such as one of NAND strings 206 ₀ to 206 _(M). Each NAND string 206 might be connected (e.g., selectively connected) to a common source (SRC) 216 and might include memory cells 208 ₀ to 208 _(N). The memory cells 208 may represent non-volatile memory cells for storage of data. The memory cells 208 of each NAND string 206 might be connected in series between a select gate 210 (e.g., a field-effect transistor), such as one of the select gates 210 ₀ to 210 _(M) (e.g., that may be source select transistors, commonly referred to as select gate source), and a select gate 212 (e.g., a field-effect transistor), such as one of the select gates 212 ₀ to 212 _(M) (e.g., that may be drain select transistors, commonly referred to as select gate drain). Select gates 210 ₀ to 210 _(M) might be commonly connected to a select line 214, such as a source select line (SGS), and select gates 212 ₀ to 212 _(M) might be commonly connected to a select line 215, such as a drain select line (SGD). Although depicted as traditional field-effect transistors, the select gates 210 and 212 may utilize a structure similar to (e.g., the same as) the memory cells 208. The select gates 210 and 212 might represent a plurality of select gates connected in series, with each select gate in series configured to receive a same or independent control signal.

A source of each select gate 210 might be connected to common source 216. The drain of each select gate 210 might be connected to a memory cell 208 ₀ of the corresponding NAND string 206. For example, the drain of select gate 210 ₀ might be connected to memory cell 208 ₀ of the corresponding NAND string 206 ₀. Therefore, each select gate 210 might be configured to selectively connect a corresponding NAND string 206 to common source 216. A control gate of each select gate 210 might be connected to select line 214.

The drain of each select gate 212 might be connected to the bit line 204 for the corresponding NAND string 206. For example, the drain of select gate 212 ₀ might be connected to the bit line 204 ₀ for the corresponding NAND string 206 ₀. The source of each select gate 212 might be connected to a memory cell 208 _(N) of the corresponding NAND string 206. For example, the source of select gate 212 ₀ might be connected to memory cell 208 _(N) of the corresponding NAND string 206 ₀. Therefore, each select gate 212 might be configured to selectively connect a corresponding NAND string 206 to the corresponding bit line 204. A control gate of each select gate 212 might be connected to select line 215.

The memory array in FIG. 2A might be a three-dimensional memory array, e.g., where NAND strings 206 may extend substantially perpendicular to a plane containing the common source 216 and to a plane containing a plurality of bit lines 204 that may be substantially parallel to the plane containing the common source 216.

Typical construction of memory cells 208 includes a data-storage structure 234 (e.g., a floating gate, charge trap, etc.) that can determine a data state of the memory cell (e.g., through changes in threshold voltage), and a control gate 236, as shown in FIG. 2A. The data-storage structure 234 may include both conductive and dielectric structures while the control gate 236 is generally formed of one or more conductive materials. In some cases, memory cells 208 may further have a defined source/drain (e.g., source) 230 and a defined source/drain (e.g., drain) 232. Memory cells 208 have their control gates 236 connected to (and in some cases form) a word line 202.

A column of the memory cells 208 may be a NAND string 206 or a plurality of NAND strings 206 selectively connected to a given bit line 204. A row of the memory cells 208 may be memory cells 208 commonly connected to a given word line 202. A row of memory cells 208 can, but need not, include all memory cells 208 commonly connected to a given word line 202. Rows of memory cells 208 may often be divided into one or more groups of physical pages of memory cells 208, and physical pages of memory cells 208 often include every other memory cell 208 commonly connected to a given word line 202. For example, memory cells 208 commonly connected to word line 202 _(N) and selectively connected to even bit lines 204 (e.g., bit lines 204 ₀, 204 ₂, 204 ₄, etc.) may be one physical page of memory cells 208 (e.g., even memory cells) while memory cells 208 commonly connected to word line 202 _(N) and selectively connected to odd bit lines 204 (e.g., bit lines 204 ₁, 204 ₃, 204 ₅, etc.) may be another physical page of memory cells 208 (e.g., odd memory cells). Although bit lines 204 ₃-204 ₅ are not explicitly depicted in FIG. 2A, it is apparent from the figure that the bit lines 204 of the array of memory cells 200A may be numbered consecutively from bit line 204 ₀ to bit line 204 _(M). Other groupings of memory cells 208 commonly connected to a given word line 202 may also define a physical page of memory cells 208. For certain memory devices, all memory cells commonly connected to a given word line might be deemed a physical page of memory cells. The portion of a physical page of memory cells (which, in some embodiments, could still be the entire row) that is read during a single read operation or programmed during a single programming operation (e.g., an upper or lower page of memory cells) might be deemed a logical page of memory cells. A block of memory cells may include those memory cells that are configured to be erased together, such as all memory cells connected to word lines 202 ₀-202 _(N) (e.g., all NAND strings 206 sharing common word lines 202). Unless expressly distinguished, a reference to a page of memory cells herein refers to the memory cells of a logical page of memory cells.

FIG. 2B is another schematic of a portion of an array of memory cells 200B as could be used in a memory of the type described with reference to FIG. 1, e.g., as a portion of array of memory cells 104. Like numbered elements in FIG. 2B correspond to the description as provided with respect to FIG. 2A. FIG. 2B provides additional detail of one example of a three-dimensional NAND memory array structure. The three-dimensional NAND memory array 200B may incorporate vertical structures which may include semiconductor pillars where a portion of a pillar may act as a channel region of the memory cells of NAND strings 206. The NAND strings 206 may be each selectively connected to a bit line 204 ₀-204 _(M) by a select transistor 212 (e.g., that may be drain select transistors, commonly referred to as select gate drain) and to a common source 216 by a select transistor 210 (e.g., that may be source select transistors, commonly referred to as select gate source). Multiple NAND strings 206 might be selectively connected to the same bit line 204. Subsets of NAND strings 206 can be connected to their respective bit lines 204 by biasing the select lines 2150-215K to selectively activate particular select transistors 212 each between a NAND string 206 and a bit line 204. The select transistors 210 can be activated by biasing the select line 214. Each word line 202 may be connected to multiple rows of memory cells of the memory array 200B. Rows of memory cells that are commonly connected to each other by a particular word line 202 may collectively be referred to as tiers.

FIG. 3 is a schematic illustrating circuitry for selective connection of a data line, for an array of memory cells as could be used in a memory of the type described with reference to FIG. 1, to a source or other circuitry of the memory. In particular, FIG. 3 depicts the selective connection of a data line 204′ to a source (e.g., common source) 216 through a transistor (e.g., an n-type field-effect transistor or nFET) 311, and the selective connection of the data line 204′ to a node 319 through a transistor (e.g., an nFET) 315. The node 319 might provide connection to peripheral circuitry of an array of memory cells. For example, the node 319 might provide connection to a page buffer, e.g., the cache register 118 and/or data register 120 of FIG. 1. The data line 204′ might represent any data line 204 of FIG. 2A or 2B, while the source 216 might represent the source 216 of FIG. 2A or 2B, for example.

The transistor 311 might selectively connect the data line 204′ to the source 26 in response to a control signal from control signal node 313 applied to the control gate of the transistor 311. The control signal node 313 may be connected to a control gate for each of a number of transistors 311 connected between other data lines 204 and the source 216. The data line 204′ might be connected to the source 216 during an erase operation, while being isolated from the node 319. The transistor 315 might selectively connect the data line 204′ to the node 319 in response to a control signal from control signal node 317 applied to the control gate of the transistor 315. The data line 204′ might be connected to the node 319 during a read operation or a programming operation, while being isolated from the source 216.

Typically, an erase operation includes a series of erase pulses applied to the NAND strings 206 through their respective data lines 204 and source 216 while voltage levels are applied to the access lines 202 sufficient to activate the corresponding memory cells. An erase verify operation may be performed between pulses to determine if the memory cells have been sufficiently erased (e.g., have threshold voltages at or below some target value). If the erase verify is failed, another erase pulse, typically having a higher voltage level, may be applied. For each pulse, the transistor 311 might be activated in response to a ramped voltage signal on the control signal node 313, e.g., a ramp from 0V to the voltage level above the voltage level the erase pulse (e.g., 24V), while a voltage of the source 216 and the data line 204′ are concurrently ramped up, e.g., a ramp from 0V to the voltage level of the erase pulse (e.g., 20V) for this example. As used herein, a first act and a second act occur concurrently when the first act occurs simultaneously with the second act for at least a portion of a duration of the second act. For example, for at least a portion of ramping up the voltage level of the data line and the source, the voltage level of the control gate of the transistor 311 is being simultaneously ramped up.

Ramping of such voltages can be generally well controlled by voltage generation devices (not shown) of a memory device. Following the erase pulse, these voltages are generally discharged to prepare for an erase verify or other subsequent access operation. The voltage level on the control signal node 313 might be allowed to electrically float while the voltage level of the data line 204′ is discharged, with an expectation that the voltage level of the control signal node 313 might follow the voltage level of the data line 204′ due to gate-drain coupling. For example, the control signal node 313 might be electrically isolated from any voltage supply, such that voltage discharge may be the result of capacitive coupling between the control signal node 313 and the data line 204′. However, depending upon the degree of coupling and other factors, variations beyond desired operating conditions might develop. For example, the voltage level of the control signal node 313 may discharge too slowly, and a voltage difference across the transistor 311 might exceed a breakdown voltage of that device. Various embodiments seek to mitigate such variations by providing control of the discharge of the control signal node 313, e.g., the voltage level to the control gate of the transistor 311.

FIG. 4 is a block schematic of circuitry for selectively controlling discharge of a control gate voltage in accordance with an embodiment. The circuitry of FIG. 4 might include a comparator (e.g., a differential amplifier) 421 ₀ having a first input (e.g., an inverting or “−” input) connected to a voltage node 423 ₀. The voltage node 423 ₀ may be capacitively coupled to the data line 204′ through a capacitance (e.g., capacitor) 427 ₀. The capacitance 427 ₀ may be connected (e.g., selectively connected) to the data line 204′. The capacitance 427 ₀ may represent one or more capacitors connected in parallel and/or series to provide a particular capacitance value Coo. The voltage node 423 ₀ may be further capacitively coupled to a reference node 435 ₀ through a capacitance (e.g., capacitor) 429 ₀. The reference node 435 ₀ might be coupled to receive a reference potential, such as a ground potential Vss or 0V. The capacitance 429 ₀ may represent one or more capacitors connected in parallel and/or series to provide a particular capacitance C₁₀. The sizing and ratio of the capacitance values C₀₀ and C₁₀ might be chosen to divide the voltage level of the data line 204′ down to a value (e.g., expected range of values) at the voltage node 423 ₀ that is suitable for operation of the comparator 421 ₀.

The voltage node 423 ₀ may further be selectively connected to a voltage node 447 ₀ through a transistor (e.g., an nFET) 445 ₀ responsive to a control signal from control signal node 449 ₀ connected to the control gate of the transistor 445 ₀. The voltage node 447 ₀ may be configured to receive a reference voltage Vrefinit0 that might represent a first threshold, e.g., a high limit. Use and determination of the reference voltage Vrefinit0 will be described infra.

The comparator 421 ₀ might have a second input (e.g., a non-inverting or “+” input) connected to a voltage node 425 ₀. The comparator 421 ₀ may be configured to provide a first logic level, e.g., a logic high level, if the voltage level at its second input is less than the voltage level at its first input, and a second logic level, e.g., a logic low level, if the voltage level at its second input is greater than the voltage level at its first input. The voltage node 425 ₀ may be capacitively coupled to the control signal node 313, and thus to a voltage level of the control gate of the transistor connected between the data line 204′ and the source 216, through a capacitance (e.g., capacitor) 431 ₀. The capacitance 431 ₀ may be connected (e.g., selectively connected) to the control signal node. The capacitance 431 ₀ may represent one or more capacitors connected in parallel and/or series to provide a particular capacitance value C₂₀. The voltage node 425 ₀ may be further capacitively coupled to a reference node 435 ₁ through a capacitance (e.g., capacitor) 433 ₀. The reference node 435 ₁ might be coupled to receive a reference potential, such as a ground potential Vss or 0V. The reference node 435 ₁ may be a same voltage node as the reference node 435 ₀. The capacitance 433 ₀ may represent one or more capacitors connected in parallel and/or series to provide a particular capacitance C₃₀. The sizing and ratio of the capacitance values C₂₀ and C₃₀ might be chosen to divide the voltage level of the control signal node 313 down to a value (e.g., expected range of values) at the voltage node 425 ₀ that is suitable for operation of the comparator 421 ₀. The sizing and ratio of the capacitance values C₂₀ and C₃₀ might be chosen to be substantially equal (e.g., equal) to the sizing and ratio of the capacitance values C₀₀ and C₁₀, respectively. The phrase “substantially equal” as used herein recognizes that even where values may be intended to be equal, variabilities and accuracies of industrial processing may lead to differences from their intended values. These variabilities and accuracies will generally be dependent upon the technology utilized in fabrication of the integrated circuit device.

The circuitry of FIG. 4 might further include a comparator (e.g., a differential amplifier) 421 ₁ having a first input (e.g., an inverting or “−” input) connected to a voltage node 425 ₁. The voltage node 425 ₁ may be capacitively coupled to the control signal node 313, and thus to a voltage level of the control gate of the transistor connected between the data line 204′ and the source 216, through a capacitance (e.g., capacitor) 431 ₁. The capacitance 431 ₁ may be connected (e.g., selectively connected) to the control signal node 313. The capacitance 431 ₁ may represent one or more capacitors connected in parallel and/or series to provide a particular capacitance value C₂₁. The voltage node 425 ₁ may be further capacitively coupled to a reference node 435 ₃ through a capacitance (e.g., capacitor) 433 ₁. The reference node 435 ₃ might be coupled to receive a reference potential, such as a ground potential Vss or 0V. The capacitance 433 ₁ may represent one or more capacitors connected in parallel and/or series to provide a particular capacitance C₃₁. The sizing and ratio of the capacitance values C₂₁ and C₃₁ might be chosen to divide the voltage level of the control signal node 313 down to a value (e.g., expected range of values) at the voltage node 425 ₁ that is suitable for operation of the comparator 421 ₁.

The comparator 421 ₁ might have a second input (e.g., a non-inverting or “+” input) connected to a voltage node 423 ₁. The comparator 421 ₁ may be configured to provide a first logic level, e.g., a logic high level, if the voltage level at its second input is less than the voltage level at its first input, and a second logic level, e.g., a logic low level, if the voltage level at its second input is greater than the voltage level at its first input. The voltage node 423 ₁ may be capacitively coupled to the data line 204′ through a capacitance (e.g., capacitor) 427 ₁. The capacitance 427 ₁ may be connected (e.g., selectively connected) to the data line 204′. The capacitance 427 ₁ may represent one or more capacitors connected in parallel and/or series to provide a particular capacitance value Col. The voltage node 423 ₁ may be further capacitively coupled to a reference node 435 ₂ through a capacitance (e.g., capacitor) 429 ₁. The reference node 435 ₂ might be coupled to receive a reference potential, such as a ground potential Vss or 0V. The reference node 435 ₂ may be a same voltage node as the reference node 435 ₃, and may further be a same voltage node as the reference nodes 435 ₀ and 435 ₁. The capacitance 429 ₁ may represent one or more capacitors connected in parallel and/or series to provide a particular capacitance C₁₁. The sizing and ratio of the capacitance values C₀₁ and C₁₁ might be chosen to divide the voltage level of the data line 204′ down to a value (e.g., expected range of values) at the voltage node 423 ₁ that is suitable for operation of the comparator 421 ₁. The sizing and ratio of the capacitance values C₀₁ and C₁₁ might be chosen to be substantially equal (e.g., equal) to the sizing and ratio of the capacitance values C₂₁ and C₃₁, respectively.

The voltage node 423 ₁ may further be selectively connected to a voltage node 447 ₁ through a transistor (e.g., an nFET) 445 ₁ responsive to a control signal from control signal node 449 ₁ connected to the control gate of the transistor 445 ₁. The voltage node 447 ₁ may be configured to receive a reference voltage Vrefinit1 that might represent a second threshold, e.g., a low limit. Use and determination of the reference voltage Vrefinit1 will be described infra. The control signal nodes 449 ₀ and 449 ₁ may be configured to receive a same control signal.

An output of the comparator 421 ₀ and an output of the comparator 421 ₁ may be connected to logic 437. The logic 437 may be any configuration of combinational and/or combinatorial logic to provide an output from logic 437 having a first logic level, e.g., a logic high level, if the comparator 421 ₀ indicates that the voltage level of the voltage node 425 ₀ is greater than the voltage level of the voltage node 423 ₀, and to provide an output from logic 437 having a second logic level, e.g., a logic low level, if the comparator 421 ₁ indicates that the voltage level of the voltage node 425 ₁ is less than the voltage level of the voltage node 423 ₁. Note that while the first and second logic levels of the comparators 421 were also described in example as corresponding to the logic high level and the logic low level, respectively, the correspondence of particular logic levels for the outputs of the comparators 421 and the logic 437 may be altered while achieving the same results.

The logic 437 might further be configured to maintain the logic level of its output if the comparator 421 ₀ indicates that the voltage level of the voltage node 425 ₀ is less than the voltage level of the voltage node 423 ₀, and the comparator 421 ₁ indicates that the voltage level of the voltage node 425 ₁ is greater than the voltage level of the voltage node 423 ₁. For example, if the logic level of the output of the logic 437 is the first logic level due to an output of the comparator 421 ₀ indicating that the voltage level of the voltage node 425 ₀ is greater than the voltage level of the voltage node 423 ₀, and a logic level of the output of the comparator 421 ₀ transitions, the logic 437 may maintain its output logic level at the first logic level until the comparator 421 ₁ indicates that the voltage level of the voltage node 425 ₁ is less than the voltage level of the voltage node 423 ₁. Conversely, if the logic level of the output of the logic 437 is the second logic level due to an output of the comparator 421 ₁ indicating that the voltage level of the voltage node 425 ₁ is less than the voltage level of the voltage node 423 ₁, and a logic level of the output of the comparator 421 ₁ transitions, the logic 437 may maintain its output logic level at the second logic level until the comparator 421 ₀ indicates that the voltage level of the voltage node 425 ₀ is greater than the voltage level of the voltage node 423 ₀. Table 1 might represent a truth table for logic 437 for such an embodiment.

TABLE 1 Comparator 421₀ Comparator 421₁ Logic 437 Logic 437 Output Output Prior Output Current Output L H X H H H H H H H L L H L X L L = logic low; H = logic high; X = do not care

The control signal node 313 may be selectively connected to the source 216 through a transistor (e.g., nFET) 441 responsive to the output of the logic 437. The voltage levels corresponding to one or more of the logic levels (e.g., the logic high level) of the output of the logic 437 may need to be transitioned to another voltage domain in order to provide an appropriate control gate voltage to control the transistor 441. Accordingly, a level shifter 439 may be included to transition the voltage levels of the logic 437 to an appropriate voltage domain. A diode-connected transistor (e.g., nFET) 443 may be included between the control signal node 313 and the transistor 441. The diode-connected transistor 443 might be used to mitigate a risk of discharging the control signal node 313 to a point where the control gate voltage of the transistor 311 falls below its threshold voltage Vt during discharge of the voltage levels of the data line 204′ and the source 216.

Through selection of particular voltage levels of the reference voltages Vrefinit0 and Vrefinit1, the comparator 421 ₀ can indicate whether the voltage level of the node 425 ₀ indicates that the voltage level of the control signal node 313 is greater than an upper limit, e.g., some voltage level in excess of the voltage level of the data line 204′ that is less than a break-down voltage of the transistor 311 of FIG. 3, while the comparator 421 ₁ can indicate whether the voltage level of the node 425 ₁ indicates that the voltage level of the control signal node 313 is less than a lower limit, e.g., some voltage level in excess of the voltage level of the data line 204′ that is greater than a threshold voltage of the transistor 311 of FIG. 3.

To determine values of Vrefinit0 and Vrefinit1, the following equations may apply: −(Vsrcinit−Vrefinit)*C1+Vrefinit*C2=−(Vsrc−Vdet_src)*C1+Vdet_src*C2  Eq. 1 Vdet_src=(C1/(C1+C2))*(Vsrc−Vsrcinit)+Vrefinit  Eq. 2 Vdet_src=Vdet_hviso  Eq. 3 Vhviso−Vsrc=Vhvisoinit−Vsrcinit+((C1+C2)/C1)*(Vrefinit−Vrefhviso)  Eq. 4

Table 2 may provide definitions of the variables of the Equations 1-4. In Table 2, the voltage node 423 may correspond to the voltage node 423 ₀ or 423 ₁; the voltage node 425 may correspond to the voltage node 425 ₀ or 425 ₁, respectively; the reference node 435 may correspond to the reference node 435 ₀ or 435 ₁, respectively; Vrefinit may correspond to the reference voltage Vrefinit0 or Vrefinit1, respectively; C1 may correspond to the capacitance value C₀₀ or C₀₁, respectively; and C₂ may correspond to the capacitance value C₁₀ or C₁₁, respectively.

TABLE 2 Variable or Constant Name Definition Vsrcinit Voltage level of the data line 204′ prior to discharge Vsrc Voltage level of the data line 204′ during discharge Vrefinit Voltage level of voltage node 423 prior to discharge of Vsrc Vdet_src Voltage level of voltage node 423 during discharge of the data line 204′ Vhvisoinit Voltage level of control signal node 313 prior to discharge Vhviso Voltage level of the control signal node 313 during discharge Vrefhviso Voltage level of voltage node 425 prior to discharge of the control signal node 313 Vdet_hviso Voltage level of voltage node 425 during discharge of the control signal node 313 C1 Capacitance value of the capacitance between the data line 204′ and the voltage node 423 C2 Capacitance value of the capacitance between the voltage node 423 and the reference node 435

With reference to Equations 1-4 and Table 2, Equation 1 describes a relationship between the voltage level of the data line 204′ and the voltage level of the voltage node 423 prior to and during discharge of the voltage level of the data line 204′. Equation 2 simplifies the equality of Equation 1. Equation 3 represents a condition at which the comparator would transition under ideal conditions. Equation 4 then represents the resulting relationship between the voltage level of the data line 204′ and the voltage level of the control signal node 313 prior to and during discharge of these voltage levels.

By selecting desired values for the quantity Vhviso−Vsrc, e.g., some value below a breakdown voltage of the transistor between the data line 204′ and the source 216 and some value above a threshold voltage of that transistor, Vrefinit0 and Vrefinit1, respectively, might be calculated based on known values of C1, C2, Vhvisoinit, Vsrcinit and Vrefhviso. As an example, if the breakdown voltage of the transistor 311 of FIG. 3 is 4V, Vhviso−Vsrc might be set to equal 3V. For an erase operation where Vhvisoinit=24V and Vsrcinit=22V, and for a configuration having capacitance values such that (C1+C2)/C1=20 producing Vrefhviso=1.00V, Vrefinit might be calculated to equal 1.05V. Accordingly, the voltage node 447 ₀ might be configured to receive a voltage level of 1.05V as Vrefinit0 to facilitate operation of the comparator 421 ₀ to indicate whether the voltage level of the control signal node 313 is deemed to be greater than 3V above the voltage level of the data line 204′.

Continuing with this example, if the threshold voltage of the transistor 311 of FIG. 3 is 1.5V, Vhviso−Vsrc might be set to equal 2V, and Vrefinit might be calculated to equal 1.00V. Accordingly, the voltage node 447 ₁ might be configured to receive a voltage level of 1.00V as Vrefinit1 to facilitate operation of the comparator 421 ₁ to indicate whether the voltage level of the control signal node 313 is deemed to be less than 2V above the voltage level of the data line 204′. Trim values indicative of the desired values of Vrefinit0 and Vrefinit1 might be stored to the trim register 128 of FIG. 1. As is known, trim values may be utilized to control an output voltage level of a voltage generation device (not shown), such as a charge pump. For various embodiments, the trim values may be utilized across the entire array of memory cells, or different portions of the array of memory cells, such as different blocks or even different data lines 204′, may have different trim values indicative of differing values of Vrefinit0 and/or Vrefinit1, e.g., where characterization of the memory device may indicate different operating characteristics of the corresponding transistors 311, different initial voltage levels, or different capacitance values, etc.

FIG. 5 is a timing diagram for use in describing operation of the circuitry of FIG. 4 in accordance with an embodiment. FIG. 5 will first be discussed with reference specifically to the comparator 421 ₀, and then its application to the comparator 421 ₁ will be discussed. In FIG. 5, the trace 551 may represent a voltage level of the voltage node 447 ₀, the trace 553 may represent a voltage level of the voltage node 423 ₀, and the trace 555 may represent a voltage level of the voltage node 425 ₀. For this example, the transistor 445 ₀ may be activated at time t0 of FIG. 5.

Comparators, such as comparator 421 ₀, may experience offsets such that their output transitions at some point other than the ideal situation where both inputs are receiving an equal voltage level. Compensation schemes are known, and might include applying a same voltage level to both inputs, and then adding or removing charge from one input until the output of the comparator transitions. With reference to FIG. 5, the period from time t0 to t1 might represent such a compensation scheme. For example, at time t0, Vrefinit may be applied to the voltage node 447 ₀, and thus the voltage node 423 ₀, at a voltage level equal to the voltage level of Vdet_hviso of the voltage node 425 ₀. Charge might then be added to the voltage node 425 ₀, for example, to cause the output of the comparator 421 ₀ to transition. Adding charge might thus result in an increase of the voltage level of the voltage node 425 ₀ as shown. The voltage node 425 ₀ might then be allowed to electrically float. For some embodiments, such compensation is not performed.

At time t1, the voltage level applied to the voltage node 447 ₀ might be set (e.g., increased) to the determined value of Vrefinit0, resulting in a corresponding increase in the voltage level of the voltage node 423 ₀. At time t2, the transistor 445 ₀ may be deactivated, thus allowing the voltage node 423 ₀ to electrically float. Discharge of the voltage level of the data line 204′, and resulting discharge of the voltage level of the control signal node 313 (e.g., the voltage level of the control gate of the transistor 311), might begin at time t3. The comparator 421 ₀ may then indicate whether the voltage level of the voltage node 425 ₀ is greater than the voltage level of the voltage node 423 ₀. In other words, the comparator 421 ₀ may provide an indication whether a difference between the voltage level of the control signal node 313 and the voltage level of the data line 204′ is deemed to be greater than some value, e.g., some upper limit.

Referring again to FIG. 5, the trace 551 may represent a voltage level of the voltage node 447 ₁, the trace 553 may represent a voltage level of the voltage node 423 ₁, and the trace 555 may represent a voltage level of the voltage node 425 ₁. For this example, the transistor 445 ₁ may be activated at time t0 of FIG. 5.

At time t0, Vrefinit may be applied to the voltage node 447 ₁, and thus the voltage node 423 ₁, at a voltage level equal to the voltage level of Vdet_hviso of the voltage node 425 ₁. Charge might then be added to the voltage node 425 ₁, for example, to cause the output of the comparator 421 ₁ to transition. Adding charge might thus result in an increase of the voltage level of the voltage node 425 ₁ as shown. The voltage node 425 ₁ might then be allowed to electrically float. For some embodiments, such compensation is not performed.

At time t1, the voltage level applied to the voltage node 447 ₁ might be set (e.g., increased) to the determined value of Vrefinit1, resulting in a corresponding increase in the voltage level of the voltage node 423 ₁. At time t2, the transistor 445 ₁ may be deactivated, thus allowing the voltage node 423 ₁ to electrically float. Discharge of the voltage level of the data line 204′, and resulting discharge of the voltage level of the control signal node 313 (e.g., the voltage level of the control gate of the transistor 311), might begin at time t3. The comparator 421 ₁ may then indicate whether the voltage level of the voltage node 425 ₀ is less than the voltage level of the voltage node 423 ₁. In other words, the comparator 421 ₁ may provide an indication whether a difference between the voltage level of the control signal node 313 and the voltage level of the data line 204′ is deemed to be less than some value, e.g., some lower limit.

FIG. 6 is a flowchart of a method of operating a memory in accordance with an embodiment. The method of FIG. 6 might occur during an erase operation, e.g., during the discharge of the erase voltages from the data line 204′ and the source 216 following an erase pulse. The method may be performed for each of a number of data lines 204′, e.g., each data line of memory cells subjected to the erase voltages, and may be performed concurrently for each of these data lines. This might be true regardless of whether each of those memory cells were selected for erase during the erase operation, e.g., where multiple blocks of memory cells share a common source 216, but may be erased individually.

At 661, a voltage level of a data line and a voltage level of a source are discharged concurrently. Discharge of the voltage level of the data line may include discharging the data line to the source through a transistor connected therebetween, e.g., transistor 311 of FIG. 3. At 663, a representation of a voltage difference between a voltage level of the data line and a voltage level of a control gate of a transistor connected between the data line and the source is monitored, e.g., concurrently with discharging the voltage level of the data line. If the voltage difference is deemed to be greater than a first value, a current path between the control gate of the transistor and the source may be activated at 665. For example, the control gate of the transistor and the source might be electrically connected. If the voltage difference is deemed to be less than a second value, the current path between the control gate of the transistor and the source may be deactivated at 667. For example, the control gate of the transistor and the source might be electrically isolated. The second value may be less than the first value, e.g., the second value may correspond to a voltage difference that is less than a voltage difference corresponding to the first value.

FIG. 7 is a flowchart of a method of operating a memory in accordance with an embodiment. The method of FIG. 7 might occur during an erase operation, e.g., during the discharge of the erase voltages from the data line 204′ and the source 216 following an erase pulse. The method may be performed for each of a number of data lines 204′, e.g., each data line of memory cells subjected to the erase voltages, and may be performed concurrently for each of these data lines. This might be true regardless of whether each of those memory cells were selected for erase during the erase operation, e.g., where multiple blocks of memory cells share a common source 216, but may be erased individually.

At 780, a first particular voltage level (e.g., Vrefinit0) is applied to a first voltage node (e.g., voltage node 423 ₀) capacitively coupled to a voltage level of a data line (e.g., data line 204′), then the first voltage node is allowed to electrically float (e.g., is electrically floated). At 782, a second particular voltage level (e.g., Vrefinit1) is applied to a second voltage node (e.g., voltage node 423 ₁) capacitively coupled to the voltage level of the data line (e.g., data line 204′), then the second voltage node is allowed to electrically float (e.g., is electrically floated). The application of the second particular voltage level at 782 may be performed prior to 780, concurrently with 780 or subsequent to 780.

At 784, e.g., while the first voltage node and the second voltage node are electrically floating, the voltage level of the data line and the voltage level of a source (e.g., source 216) are concurrently discharged.

At 786, e.g., while discharging the voltage level of the data line and the voltage level of the source, a voltage level of the first voltage node is compared to a voltage level of a third voltage node (e.g., voltage node 425 ₀) capacitively coupled to a voltage level (e.g., of control signal node 313) of a control gate of a transistor (e.g., transistor 311) connected between the data line and the source. At 788, e.g., while discharging the voltage level of the data line and the voltage level of the source, a voltage level of the second voltage node is compared to a voltage level of a fourth voltage node (e.g., voltage node 425 ₁) capacitively coupled to a voltage level (e.g., of control signal node 313) of the control gate of the transistor connected between the data line and the source.

At 790, e.g., while discharging the voltage level of the data line and the voltage level of the source, a current path (e.g., transistor 441) between the source and the control gate of the transistor connected between the data line and the source may be activated while the voltage level of the third voltage node is deemed to be greater than the voltage level of the first voltage node. At 792, e.g., while discharging the voltage level of the data line and the voltage level of the source, the current path between the source and the control gate of the transistor connected between the data line and the source may be deactivated while the voltage level of the fourth voltage node is deemed to be less than the voltage level of the second voltage node.

CONCLUSION

Although specific embodiments have been illustrated and described herein, it will be appreciated by those of ordinary skill in the art that any arrangement that is calculated to achieve the same purpose may be substituted for the specific embodiments shown. Many adaptations of the embodiments will be apparent to those of ordinary skill in the art. Accordingly, this application is intended to cover any adaptations or variations of the embodiments. 

What is claimed is:
 1. An integrated circuit device, comprising: a first node; a second node; a transistor connected between the first node and the second node; a current path between a control gate of the transistor and the second node; and a controller, wherein the controller is configured to: concurrently discharge a voltage level of the first node and a voltage level of the second node; monitor a representation of a voltage difference between the voltage level of the first node and a voltage level of the control gate of the transistor while discharging the voltage level of the first node and discharging the voltage level of the second node; activate the current path if the voltage difference is deemed to be greater than a first value; and deactivate the current path if the voltage difference is deemed to be less than a second value.
 2. The integrated circuit device of claim 1, wherein the controller being configured to monitor the representation of the voltage difference between the voltage level of the first node and the voltage level of the control gate of the transistor comprises the controller being configured to: monitor an output of a first comparator having a first input capacitively coupled to the first node and a second input capacitively coupled to the control gate of the transistor, wherein the output of the first comparator is configured to indicate whether the voltage difference is deemed to be greater than the first value; and monitor an output of a second comparator having a first input capacitively coupled to the control gate of the transistor and a second input capacitively coupled to the first node, wherein the output of the second comparator is configured to indicate whether the voltage difference is deemed to be less than the second value.
 3. The integrated circuit device of claim 1, wherein the controller, after activating the current path if the voltage difference is deemed to be greater than the first value, is further configured to: maintain activation of the current path if the voltage difference is no longer deemed to be greater than the first value and the voltage difference is deemed to be greater than the second value.
 4. The integrated circuit device of claim 3, wherein the controller, after deactivating the current path if the voltage difference is deemed to be less than the second value, is further configured to: maintain deactivation of the current path if the voltage difference is no longer deemed to be less than the second value and the voltage difference is deemed to be less than the first value.
 5. The integrated circuit device of claim 1, wherein the first value is selected such that the controller is configured to activate the current path before the voltage difference is deemed to be greater than a breakdown voltage of the transistor, and wherein the second value is selected such that the controller is configured to deactivate the current path before the voltage difference is deemed to be less than a threshold voltage of the transistor.
 6. The integrated circuit device of claim 1, wherein the transistor is a first transistor, and wherein the current path comprises: a second transistor connected between the second node and the control gate of the first transistor; and a third transistor connected between the second transistor and the control gate of the first transistor; wherein a control gate of the third transistor is connected to the control gate of the first transistor; wherein the controller is configured to activate the current path by activating the second transistor; and wherein the controller is configured to deactivate the current path by deactivating the second transistor.
 7. An integrated circuit device, comprising: a first node; a second node selectively connected to the first node through a transistor; a first voltage node capacitively coupled to a voltage level of the first node; a second voltage node capacitively coupled to the voltage level of the first node; a third voltage node capacitively coupled to a voltage level of a control gate of the transistor; a fourth voltage node capacitively coupled to the voltage level of the control gate of the transistor; a current path between the second node and the control gate of the transistor; and a controller configured to: apply a first voltage level to the first voltage node, then allow the first voltage node to electrically float; apply a second voltage level, lower than the first voltage level, to the second voltage node, then allow the second voltage node to electrically float; concurrently discharge the voltage level of the first node and a voltage level of the second node; compare a voltage level of the first voltage node to a voltage level of the third voltage node; compare a voltage level of the second voltage node to a voltage level of the fourth voltage node; activate the current path while the voltage level of the third voltage node is deemed to be greater than the voltage level of the first voltage node; and deactivate the current path while the voltage level of the fourth voltage node is deemed to be less than the voltage level of the second voltage node.
 8. The integrated circuit device of claim 7, wherein the controller is configured to apply the second voltage level to the second voltage and to apply the first voltage level to the first voltage node concurrently.
 9. The integrated circuit device of claim 7, wherein the controller being configured to discharge the voltage level of the first node comprises the controller being configured to discharge the voltage level of the first node to the second node through the transistor.
 10. The integrated circuit device of claim 7, wherein the controller is further configured to: electrically float the first voltage node and electrically float the third voltage node while comparing the voltage level of the first voltage node to the voltage level of a third voltage node; and electrically float the second voltage node and electrically float the fourth voltage node while comparing the voltage level of the second voltage node to the voltage level of the fourth voltage node.
 11. The integrated circuit device of claim 10, wherein the controller is further configured to: adjust a level of charge on the third voltage node prior to applying the first voltage level to the first voltage node, and prior to electrically floating the third voltage node; and adjust a level of charge on the fourth voltage node prior to applying the second voltage level to the second voltage node, and prior to electrically floating the fourth voltage node.
 12. The integrated circuit device of claim 7, wherein the transistor is a first transistor, and wherein the current path comprises: a second transistor between the second node and the control gate of the transistor; wherein activating the current path comprises activating the second transistor; and wherein deactivating the current path comprises deactivating the second transistor.
 13. The integrated circuit device of claim 7, wherein the first voltage level is selected such that the voltage level of the third voltage node would be deemed to be greater than the voltage level of the first voltage node before a voltage difference between the voltage level of the control gate of the transistor and the voltage level of the first node exceeds a breakdown voltage of the transistor, and wherein the second voltage level is selected such that the voltage level of the fourth voltage node would be deemed to be less than the voltage level of the second voltage node before a voltage difference between the voltage level of the control gate of the transistor and the voltage level of the first node is less than a threshold voltage of the transistor.
 14. An integrated circuit device, comprising: a first node; a second node selectively connected to the first node through a transistor; a first comparator having a first input capacitively coupled to the first node, a second input capacitively coupled to a control gate of the transistor, and an output; a second comparator having a first input capacitively coupled to the control gate of the transistor, a second input capacitively coupled to the first node, and an output; a first voltage node connected to the first input of the first comparator, and capacitively coupled to a first reference node; a second voltage node connected to the second input of the second comparator, and capacitively coupled to a second reference node; a third voltage node connected to the second input of the first comparator, and capacitively coupled to a third reference node; a fourth voltage node connected to the first input of the second comparator, and capacitively coupled to a fourth reference node; a fifth voltage node selectively connected to the first voltage node and configured to receive a first reference voltage; a sixth voltage node selectively connected to the second voltage node and configured to receive a second reference voltage; a logic having a first input connected to the output of the first comparator and a second input connected to the output of the second comparator, and having an output configured to provide a first logic level when the output of the first comparator indicates that a voltage level of its second input is greater than a voltage level of its first input, and to provide a second logic level, different from the first logic level, when the output of the second comparator indicates that a voltage level of its first input is less than a voltage level of its second input; and a current path between the second node and the control gate of the transistor, wherein the current path is configured to be activated in response to the output of the logic having the first logic level, and to be deactivated in response to the output of the logic having the second logic level.
 15. The integrated circuit device of claim 14, wherein the logic is further configured to maintain the first logic level at its output if the output of the first comparator transitions to indicate that the voltage level of its second input is no longer greater than the voltage level of its first input while the output of the second comparator indicates that the voltage level of its first input is greater than the voltage level of its second input, and to maintain the second logic level at its output if the output of the second comparator transitions to indicate that the voltage level of its first input is no longer less than the voltage level of its second input while the output of the first comparator indicates that the voltage level of its second input is less than the voltage level of its first input.
 16. The integrated circuit device of claim 14, wherein the first reference node, the second reference node, the third reference node and the fourth reference node are each configured to receive a particular voltage level.
 17. The integrated circuit device of claim 16, wherein the particular voltage level is a ground potential.
 18. The integrated circuit device of claim 14, wherein the first comparator comprises a first differential amplifier, wherein the second comparator comprises a second differential amplifier, wherein the first input of the first comparator is an inverting input of the first differential amplifier, and wherein the first input of the second comparator is an inverting input of the second differential amplifier.
 19. The integrated circuit device of claim 14, wherein the transistor is a first transistor, and wherein the current path comprises a second transistor connected between second node and the control gate of the first transistor, the integrated circuit device further comprising: a level shifter configured to transition a voltage level of the output of the logic to a voltage domain configured to activate the second transistor when the output of the logic has the first logic level, and to deactivate the second transistor when the output of the logic has the second logic level.
 20. The integrated circuit device of claim 19, wherein the current path further comprises a diode-connected third transistor connected between the second transistor and the control gate of the first transistor, and configured to mitigate a risk of discharging the voltage level of the control gate of the first transistor below a threshold voltage of the first transistor. 